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TK10931V
NARROW BAND FM/AM IF SYSTEM FEATURES
s s s s s s s s s
Simultaneous Operation (AM Section, FM Section) AM Section with ON/OFF Control Input AGC Amplifier Control Input AGC Amplifier Output High-speed FM Limiter Amplifier (Up to 11 MHz) RF AGC Output (for External RF Amplifier) Built-in Noise Squelch Circuit (Noise Amplifier, Rectifier, Comparator) Wide Range Voltage Operation (2.5 V to 8.5 V) Very Small Package (TSSOP-24)
APPLICATIONS
s s s s
Amateur Radios CB Radios Utility Radios Scanner Receivers
TK10931V
OSC(B) OSC(E) MIX OUTPUT VCC AM IF INPUT
RF INPUT GND COMP OUTPUT COMP INPUT NOISE AMP OUTPUT NOISE AMP INPUT AM AGC INPUT AGC AMP OUTPUT RF AGC OUTPUT RSSI OUTPUT AM SW AM DET OUT
DESCRIPTION
The TK10931V is an IF system IC designed for communications equipment. The TK10931V contains the following functions: Oscillator Mixer FM IF Limiter Quadrature Detector AM AGC Amplifier Squelch Noise Amplifier AM Detector Squelch Rectifier RSSI Output RF AGC Output Squelch Comparator The TK10931V is suited for Amateur radios, CB radios, and Wide-Band receivers.
COMP OUTPUT
DECOUPLING FM IF INPUT DECOUPLING DECOUPLING LIM OUTPUT QUAD INPUT FM DET OUTPUT
BLOCK DIAGRAM
NOISE AMP OUTPUT AGC AMP OUTPUT NOISE AMP INPUT RF AGC OUTPUT
AM AGC INPUT
RSSI OUTPUT
COMP INPUT
The TK10931V is available in the very small TSSOP-24 surface mount package.
COMP
Vref
RECT AMP
AGC
VCC
AM DET
ORDERING INFORMATION
AM AMP RSSI OSC MIXER FM DET
TK10931V
Tape/Reel Code
TAPE/REEL CODE
TL: Tape Left
January 2001 TOKO, Inc.
Page 1
FM DET OUTPUT
MIX OUTPUT
DECOUPLING
DECOUPLING
DECOUPLING
QUAD INPUT
OSC(B)
OSC(E)
VCC
LIM OUTPUT
FM IF INPUT
AM IF INPUT
AM DET OUT
RF INPUT
AM SW
GND
TK10931V
ABSOLUTE MAXIMUM RATINGS
Supply Voltage ......................................................... 10 V Operating Voltage Range ............................... 2.5 to 8.5 V Power Dissipation (Note 1) ................................. 230 mW FM Limiter Amp Input Frequency ......................... 11 MHz AM AGC Amp Input Frequency ........................... 0.5 MHz Mixer Input Frequency ....................................... 150 MHz Storage Temperature Range ..................... -55 to +150 C Operating Temperature Range .................... -30 to +85 C
TK10931V ELECTRICAL CHARACTERISTICS
Test Conditions: VCC = 3.0 V, TA = 25 C, unless otherwise specified.
SYMBOL ICC GM RIM PARAMETER Supply Current No Input, AM OFF Mixer Conversion Gain Mixer Input Resistance Using CFU455F DC Measurement 3.7 22 3.6 5.0 mA dB k TEST CONDITIONS No Input, AM ON MIN TYP 5.3 MAX 7.1 UNITS mA
FM PORTION SINAD VOUT(DET)1 THD1 Gf SH SL HYS 12 dB SINAD Demodulation Output Voltage 1 Total Harmonic Distortion Filter Amplifier Gain SCAN Control High Level SCAN Control Low Level Squelch Hysteresis No Input VRSSI RSSI Output Voltage VIN = +40 dB VIN = +100 dB RFAGC RF Automatic Gain Control RF AGC OUT V16 = 1 V 0.0 0.4 1.0 62 3 kHz DEV +80 dB, 3 kHz DEV +80 dB fIN = 1 kHz, Rf = 270 k, RIN = 1 k Squelch Input 2.5 V Squelch Input 0 V 67 0.1 0.8 1.4 69 0.5 1.2 1.8 76 2.5 0.3 55 11 80 1.0 47 18 105 2.0 dB mVrms % dB V V mV V V V dB
Note 1: Power dissipation is 230 mW in free air. Derate at 1.84 mW/C for operation above 25 C. Note 2: If the ambient temperature falls below -10 C, the harmonic distortions of the AM detector output are increased; the minimum operation voltage will be set to 2.7 V.
Page 2
January 2001 TOKO, Inc.
TK10931V
TK10931V ELECTRICAL CHARACTERISTICS (CONT.)
Test Conditions: VCC = 3.0 V, TA = 25 C, unless otherwise specified.
SYMBOL AM PORTION S VOUT(DET)2 THD2 THD3 vol(AGC) VOFF VON
PARAMETER
TEST CONDITIONS
MIN
TYP
MAX
UNITS
Sensitivity Demodulation Output Voltage Total Harmonic Distortion 2 Total Harmonic Distortion 3 AGC Amplifier Output Level AM OFF Voltage AM ON Voltage
Input Level when Output Level = 20 mVrms 1 kHz 30%, VIN = +60 dB 1 kHz 30%, VIN = +60 dB 1 kHz 80%, VIN = +60 dB Non Modulation VIN = +60 dB 500 -0.3 0.8VCC 35
16 50 1.0 2.0
23 65 2.0 4.0
dB mV % % mVP-P
0.3
V
January 2001 TOKO, Inc.
Page 3
TK10931V
TEST CIRCUIT
VCC 51 ~ 10 F 10.7 MHz + 0.01 F 30 k 51 k 1 F + 270 k 1 F + 1 k 20 k + 10 F 0.1 F 0.1 F 0.01 F 10 k 20 k 10 k VCC 8.2 k
COMP
AMP
Vref
ECT
OSC
~
MIXER
33 pF 0.1 F 10.245 MHz 120 pF 10 pF 0.1 F 0.1 F 0.1 F 30 k CFU455F
0.01 F
Page 4
+
+ -
AGC
AM DET
RSSI
10 k
0.01 F
7BRE-7437Z VCC 10 F
0.1 F
January 2001 TOKO, Inc.
TK10931V
TYPICAL PERFORMANCE CHARACTERISTICS
0 -20
OUTPUT VOLTAGE vs. INPUT VOLTAGE
-60
OUTPUT VOLTAGE vs. OSCILLATING VOLTAGE
-70
Desired fIN = 10.700 MHz
VOUT (dBm)
-40 -60 -80
VOUT (dBm)
3rd Order Intermod fIN1 = 10.699 MHz fIN2 = 10.698 MHZ
-80
-90
-100 0 20 40 60
80
100
120
-100 -40
-30
VIN (dB)
-20 -10 0 VOSC (dB)
10
20
-40
OUTPUT VOLTAGE vs. INPUT FREQUENCY (fIF - 455 kHz) 0 -20
S+N+D, N, and THD vs. INPUT VOLTAGE
20 16 12 8
S+N+D
S+N+D,N (dBm)
-60 VOUT (dBm)
-40 -60
THD
-80
-100
-80 -120 1 10 100 1000 fIN (MHz) -100 -20
N
4
0
20
40 60 80 VIN (dB)
0 100 120
FM DETUNE CHARACTERISTICS 1000 1000
2.5 2.0
S-CURVE
VOUT (mVrms)
100
VOUT
100
THD (%) VDC (V)
1.5 1.0 0.5 0.0 -60
10
10
1
THD
1
0.1 -15
-10
-5
0 f (kHz)
5
10
0.1 15
-40
-20
0 f (kHz)
20
40
60
January 2001 TOKO, Inc.
THD (%)
VCC = 9.0 V VCC = 3.0 V VCC = 2.3 V
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TK10931V
TYPICAL PERFORMANCE CHARACTERISTICS (CONT.)
RF AGC RSSI
0
FM DET
FM OUTPUT VOLTAGE vs. INPUT FREQUENCY
Rd = 30 k DEV = 3 kHz
FM AMP
-20
10 k
VOUT (dBm)
~
0.1 F
0.1 F
0.1 F
10 pF 0.01F 30 k V
-40
VCC 4.7 H + 10 F
7BRE-7437Z 0.1 F
-60
Rd = 30 k // 1 k DEV = 15 kHz
S-CURVE MEASUREMENT CIRCUIT (f IN = 455 kHz)
-80 1 10 100 fIN (kHz) 1000
AM DETECTOR OUTPUT vs. MIXER INPUT 0 -20
S+N+D,N (dBm)
AM DEMODULATION DETUNING
20 16
THD (%)
1000
1000
S+N+D
VOUT (mVrms)
100
VOUT
100
-40 -60
N
12 8
THD2 THD1
10
10
-80 -100 -20
1
4
THD
1
0
20
40 60 80 VIN (dB)
0 100 120
0.1 -20
-10
0 f (kHz)
10
0.1 20
0 -20
VOUT (dBm)
AGC AMP OUTPUT VOLTAGE vs. INPUT VOLTAGE
CARRIER
2.0 1.6 VOUT (V) 1.2 0.8 0.4
RSSI OUTPUT VOLTAGE vs. INPUT VOLTAGE
-40 -60
DISTORTION
VCC = 9.0 V VCC = 3.0 V
-80 -100 -20
VCC = 2.3 V
0
20
40 60 80 100 VIN (dB)
120
0.0 -20
0
20
40 60 80 100 VIN (dB)
120
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January 2001 TOKO, Inc.
THD (%)
TK10931V
TYPICAL PERFORMANCE CHARACTERISTICS (CONT.)
2.0 1.6 VOUT (V) 1.2 0.8 0.4 0.0 -20
RSSI OUTPUT VOLTAGE vs. INPUT VOLTAGE
-40 C +25 C +85 C
2.0 1.6
VOUT (V)
RF AGC OUTPUT VOLTAGE vs. INPUT VOLTAGE
VCC = 2.3 V VCC = 3.0 V VCC = 9.0 V
1.2 0.8 0.4 0.0 -20
0
20
40 60 80 100 VIN (dB)
120
0
20
40 60 80 100 VIN (dB)
120
2.0 1.6 VOUT (V) 1.2 0.8 0.4 0.0 -20
RF AGC OUTPUT VOLTAGE vs. INPUT VOLTAGE
-40 C +25 C +85 C
2.0 1.6 VOUT (V) 1.2 0.8 0.4
RECTIFIER OUTPUT VOLTAGE vs. MIXER INPUT LEVEL
VCC = 2.4 V VCC = 3.0 V VCC = 9.0 V
0
20
40 60 80 100 VIN (dB)
120
0.0 -20
0
20
40 60 80 100 VIN (dB)
120
1 k 330 pF
8.2 k AF OUT 0.01 F 20 k 100 pF
RECTIFIER CIRCUIT FREQUENCY RESPONSE
MIXER INPUT FREQUENCY = 10.7 MHz MOD DEV = 3 kHz fIN = 1 kHz
VCC 20 k 100 pF 30 k
10 0
RECT
+ +
VOUT (dBV)
-10 -20 -30 -40 -50
Vref
Vref
TK10931V + 51 k
1 F
RECTIFIER VOLTAGE MEASUREMENT CIRCUIT
1
10
100 fIN (kHz)
1000
January 2001 TOKO, Inc.
Page 7
TK10931V
TYPICAL PERFORMANCE CHARACTERISTICS (CONT.)
1 F
20 k
20 k
10 8
RECT
SUPPLY CURRENT vs. SUPPLY VOLTAGE
ICC (mA)
RECTIFIER FREQUENCY MEASUREMENT CIRCUIT
1.4 1.2
VHYS VH VL
+
+
Vref
51 k
+ 1 F
6 4
AM ON
TK10931V
AM OFF
2 0 0 2 4 6 VCC (V) 8 10
VHYS, COMP IN (V) vs. SUPPLY VOLTAGE
FM OUTPUT VOLTAGE, 12 dB SINAD vs. SUPPLY VOLTAGE 100 200 160 80 60 40 20 0 10
VHYS, COMP IN (V)
1.0 VOUT (mV) 0.8 0.6
VL VH
120 80 40
VOUT DEV = 3 kHz
0.4 0.2
VHYS
12 dB SINAD
0 0 2 4 6 VCC (V) 8 10
0 0 2 4 6 VCC (V) 8
2.0 1.6
THD (%)
TOTAL HARMONIC DISTORTION vs. SUPPLY VOLTAGE
AM OUTPUT VOLTAGE vs. SUPPLY VOLTAGE 200 160
VOUT (mV)
VOUT DEV = 80%
100 80 60 40
VOUT DEV = 30%
1.2 0.8 0.4
THD (%)
120 80 40
20 mVrms VOUT
20 0 10
0.0 0 2 4 6 VCC (V) 8 10
0 0 2 4 6 VCC (V) 8
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January 2001 TOKO, Inc.
20 mVrms VOUT (dB)
12 dB SINAD (dB)
TK10931V
TYPICAL PERFORMANCE CHARACTERISTICS (CONT.)
TOTAL HARMONIC DISTORTION vs. SUPPLY VOLTAGE 2.0 1.6
THD (%)
1.2 0.8
THD (DEV = 30%)
0.4
THD (DEV = 80%)
0.0 0 2 4 6 VCC (V) 8 10
RSSI, RFAGC TRANSIENT RESPONSE
RSSI
RSSI Output
RFAGC
RFAGC Output
10 k
CL
PIN 15 AND 16 EXTERNAL COMPONENTS
10 k
CL
RSSI ON/OFF
RSSI OUTPUT VOLTAGE TRANSIENT RESPONSE (MIXER INPUT ON/OFF)
* CL = 560 pF (RISE)
A2 3.90 V DLY 493.4 ms 100% 90% A2 3.90 V
(FALL)
DLY 986.0 ms
10% 0% > 20 mV 5 sec/div > 20 mV 5 sec/div
Rise Time: 12.5 sec
Fall Time: 16.0 sec
January 2001 TOKO, Inc.
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TK10931V
RSSI ON/OFF (CONT)
* CL = 0.1 F (RISE)
A2 3.90 V DLY 28.20 ms 100% 90% A2 3.90 V
(FALL)
DLY 38.19 ms
10% 0% > 20 mV 1 msec/div > 20 mV 1 msec/div
Rise Time: 2.0 msec
Fall Time: 2.2 msec
RSSI OUTPUT VOLTAGE TRANSIENT RESPONSE (POWER SUPPLY VOLTAGE ON/OFF)
* CL = 560 pF (RISE)
DELAY 18.52 ms 100% 90% DELAY
(FALL)
29.86 ms
10% 0% > .2 V= 0.5 msec/div > .2 V= 0.1 sec/div
Rise Time: 1.1 msec
Fall Time: 12.0 sec
* CL = 0.1 F (RISE)
DELAY 15.73 ms 100% 90% DELAY
(FALL)
26.28 ms
10% 0% > .2 V= 1 msec/div > .2 mV= 1 msec/div
Rise Time: 2.6 msec
Fall Time: 1.6 msec
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January 2001 TOKO, Inc.
TK10931V
RFAGC ON/OFF
RFAGC OUTPUT VOLTAGE TRANSIENT RESPONSE (MIXER INPUT ON/OFF)
* CL = 560 pF (RISE)
A2 3.90 V DLY 494.8 ms 100% 90% A2 3.90 V
(FALL)
DLY 990.4 ms
10% 0% > 20 mV 5 sec/div > 20 mV 5 sec/div
Rise Time: 12.5 sec
Fall Time: 13.0 sec
* CL = 0.1 F (RISE)
A2 3.90 V DLY 7.955 ms 100% 90% A2 3.90 V
(FALL)
DLY 38.21 ms
10% 0% > 20 mV 1 msec/div > 20 mV 1 msec/div
Rise Time: 2.2 msec
Fall Time: 2.2 msec
RFAGC OUTPUT VOLTAGE TRANSIENT RESPONSE (POWER SUPPLY VOLTAGE ON/OFF)
* CL = 560 pF (RISE)
DELAY 19.93 ms 100% 90% DELAY
(FALL)
29.86 ms
10% 0% > .2 V= 5 sec/div > .2 V= 10 sec/div
Rise Time: 8.0 sec
Fall Time: 12.0 sec
January 2001 TOKO, Inc.
Page 11
TK10931V
RFAGC ON/OFF (CONT)
* CL = 0.1 F (RISE)
DELAY 17.15 ms 100% 90% DELAY
(FALL)
27.06 ms
10% 0% > .2 V= 1 msec/div > .2 V= 1 msec/div
Rise Time: 2.2 msec
Fall Time: 1.6 msec
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January 2001 TOKO, Inc.
TK10931V
PIN FUNCTION DESCRIPTION
PIN NO. 1 2 SYMBOL OSC(B) OSC(E) VOLTAGE 2.98 V 2.2 V
VCC 10 k
INTERNAL EQUIVALENT CIRCUIT
DESCRIPTION Pins 1 and 2 can be used to build a colpitts type oscillator. The emitter-follower operating current can be increased by connecting an external resistor between Pin 2 and GND when the load is heavy. Inject the oscillating signal into Pin 1 by capacitive decoupling with Pin 2 OPEN when an external oscillator is used instead of the internal oscillator. Mixer Output Terminal. The output impedance is approximately 1.8 k.
3 pF 3.9 k 150 A
3
MIX OUTPUT
1.6 V
VCC
1.8 k 260 A
4 5
VCC AM IF INPUT
3.0 V 1.9 V
VCC
Power Supply Terminal AM AGC Amplifier Signal Input Terminal
10 k
6
DECOUPLING
1.2 V
25 A
VCC
AM AGC Amplifier Decoupling Terminal
7 8 9
FM IF INPUT DECOUPLING DECOUPLING
2.0 V 2.0 V 2.0 V
VCC
1.8 k 80 A
Pin 7 is the FM IF Limiter Amplifier Signal Input Terminal. The input impedance is approximately 1.8 k9. Pins 8 and 9 are the FM Limiter Amplifier Decoupling Terminals.
January 2001 TOKO, Inc.
Page 13
TK10931V
PIN FUNCTION DESCRIPTION (CONT.)
PIN NO. 10 SYMBOL LIM OUTPUT VOLTAGE 2.0 V INTERNAL EQUIVALENT CIRCUIT
VCC
DESCRIPTION FM Limiter Amplifier Signal Output Terminal. This pin connects to the phase shifter circuit.
160 A
11
QUAD INPUT
3.0 V
VCC
The Phase Shifter Connecting Terminal
40 A
12
FM DET OUTPUT
1.3 V
100 k
VCC
FM Detected Signal Output Terminal
100 k
20 pF
120 A
13
AM DET
1.3 V
90 A
VCC
AM Detected Signal Output Terminal
14
AM SW
51 k
AM AGC Amplifier ON/OFF Control Terminal. The AM IF, AGC, and Detector circuits are in the active state when Pin 14 is pulled up to VCC. The AM IF, AGC, and Detector circuits are in the standby state when Pin 14 is pulled down to GND. RSSI Signal Output Terminal
15
RSSI OUTPUT
VCC
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January 2001 TOKO, Inc.
TK10931V
PIN FUNCTION DESCRIPTION (CONT.)
PIN NO. 16 SYMBOL RF AGC OUTPUT VOLTAGE INTERNAL EQUIVALENT CIRCUIT
VCC
DESCRIPTION RF AGC Signal Output Terminal
17
AGC AMP OUTPUT
1.1 V
100 k
VCC
AM AGC Amplifier Signal Output Terminal. Maximum output current is up to 1 mA.
100 k
18
AM AGC INPUT
20 A
VCC
AM AGC Amplifier Gain Control Terminal
19
NOISE AMP INPUT
1.5 V
VCC 20 A VCC/2
Noise Amplifier Signal Input Terminal for the Squelch
20
NOISE AMP OUTPUT
1.5 V
VCC
51 k
Noise Amplifier Signal Output and Rectifier Circuit Signal Input Terminal for the Squelch
21
COMP INPUT
VCC 20 A
Rectifier Circuit Signal Output and Comparator Signal Input Terminal for Squelch
January 2001 TOKO, Inc.
Page 15
TK10931V
PIN FUNCTION DESCRIPTION (CONT.)
PIN NO. 22 SYMBOL COMP OUTPUT VOLTAGE INTERNAL EQUIVALENT CIRCUIT
VCC 20 A
DESCRIPTION Comparator Signal Output Terminal for Squelch
5k
100 k
23 24
GND RF INPUT
0V 1.0 V
VCC 3.6 k
GND Terminal Mixer Signal Input Terminal
260 A
3.6 k 30 pF
1V
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January 2001 TOKO, Inc.
TK10931V
CIRCUIT DESCRIPTION
The TK10931V has various functions that include a mixer up to 150 MHz, and independent AM IF and FM IF stages. This makes the TK10931V suitable for a communications receiver as described in the following. The FM-IF stage is always in operation, but the AM-IF stage is available with an ON/OFF function. The AM-IF signal is available from a buffered output in front of the AM detector. Its output signal is available for an external detector such as a product detector. In addition, the RF AGC output for an external RF stage and a built-in rectifier for noise squelch are available. As a result, the application circuit can be simple. The RSSI output is implemented with wide dynamic range and excellent temperature characteristics. The Mixer is implemented with wide dynamic range in spite of high gain. (1) Mixer, Oscillator The Mixer consists of a Gilbert multiplier, Oscillator, and IF amplifier. The Mixer circuit is optimized, resulting in a wide dynamic range in spite of a high transfer gain (22 dB). The Noise Figure is approximately 10 dB under input impedance matching conditions. The frequency response as a function of input impedance is shown in Figure 1.
Frequency (MHz) 10
50 -j10 -j25 -j50 -j100 -j250 100 250 f = 10 MHz 30 MHz 50 MHz 100 MHz 150 MHz
Input Impedance Rp() 3878 3532 2893 2889 2620 2458 2128 Cp(pf) 3.90 3.50 3.24 3.06 3.10 3.12 3.04
20 30 50 70
Mixer Input
S11
100 150
FIGURE 1
The built-in oscillator circuit consists of a general Colpitts type oscillator with the collector grounded. The operating current of the oscillator is 100 A. As shown later, operating above tens of MHz is possible by increaing the Gm of the oscillator with an externally connected resistor. Figure 2 illustrates general Colpitts type oscillators. Various resonators my be used, for instance, L/C, crystal, ceramic, SAW, and others.
January 2001 TOKO, Inc.
Page 17
TK10931V
CIRCUIT DESCRIPTION (CONT.)
VCC VCC VCC
Crystal Resonator
LC Resonator
SAW Resonator
FIGURE 2: EXAMPLES FOR COLPITTS TYPE OSCILLATOR
External Injection If an external oscillator is used instead of the internal oscillator, inject the oscillating signal into Pin 1 by a capacitor connection. Pin 2 must be opened, as shown in Figure 3. In this case, the multiplier sees the oscillator being operated as an emitter follower.
VCC
Pin 2 must be open
FIGURE 3: EXAMPLE FOR EXTERNAL OSCILLATOR Overtone Oscillation When operating an overtone oscillation above 30 MHz using a crystal resonator, design using the circuit shown in Figure 5 to reduce the fundamental mode. When the operation frequency is higher, it is possible that the Gm of the oscillator may be insufficient and the oscillating amplitude will be down. This can be improved by connecting an external resistor between Pin 2 and GND to increase the operating current.
Page 18
January 2001 TOKO, Inc.
TK10931V
CIRCUIT DESCRIPTION (CONT.)
VCC
F(osc) is the fundamental frequency of the crystal resonator. 3 x F(osc) is the 3rd overtone frequency of the crystal resonator. Moreover, it is established that the series value of the equivalent capacitance of the circuit is in the dotted line of Figure 4 and capacitance C1 is the load capacitance of the crystal resonator. When the operating current of the oscillator is insufficient, increase Gm of the oscillator by the external resistor RE. In this case, the increased operating current (Ie) of the oscillator is calculated by the following: Ie(mA) = VCC(V) - 0.7
C1
X'tal
C3
L
C2
200 A
RE
FIGURE 4: EXAMPLE FOR OVERTONE OSCILLATION
+j
Reactance
FA
FB Frequency
-j
FIGURE 5
RE(K) (2) RF AGC Output For manufacturers with equipment requiring external RF amplifiers, etc., the RF-AGC output terminal is readily available. Because this AGC output is picked out from the first stage of the FM-IF portion, the AGC output is not affected by the AM switch when stopping the AM-IF operation. Therefore, when receiving an FM signal, its output contributes to improving strong input characteristics. Its output is implemented as a current output from the collector of the PNP-transistor. Therefore, its current is converted into a voltage with an external resistor. A composite example is shown as Figure 6. A receiver circuit example in CB radios is shown at "CB Radio Application" of the Application Information section. The example in Figure 6 controls the gain by changing the bias voltage of the RF-AMP with the output of transistor QA1 that is driven with the RF-AGC output of Pin 16.
VCC VCC RF-AMP VCC
The constants of the circuit in the dotted line of Figure 4 establish that the condition of oscillation is met for the 3rd overtone frequency only. Figure 5 shows the characteristics of the impedance of the two terminals versus frequency of this circuit. The condition of oscillation is the capacitance at the overtone frequency and the inductance at near-fundamental frequency. Therefore, when it is established that the fundamental frequency is included between FA and FB and that the overtone frequency is above FB, the condition of 3 times overtone is: F(osc) > FA FA = 2 1 LC3 FB = FA 3 x F(osc) > FB, 1+ C2 C3
QA1
AGC Line
FIGURE 6: EXAMPLE FOR EXTERNAL AGC AMPLIFIER
January 2001 TOKO, Inc.
Page 19
TK10931V
CIRCUIT DESCRIPTION (CONT.)
(3) FM-IF Limiter Amplifier, RSSI The IF limiter amplifier is composed of 6 differential gain stages. The total gain of the IF limiter amplifier is 80 dB at 455 kHz. The output signal of the IF limiter amplifier is provided at Pin 10 through the emitter-follower output stage. The IF limiter amplifier output level is 0.5 VP-P. The operating current of the emitter-follower at the IF limiter amplifier is 200 A. If the capacitive load is heavy, the negative half cycle of the output waveform may be distorted. This can be improved by connecting an external resistor between Pin 10 and GND to increase the operating current. The increased operating current by an external resistor is calculated as follows (see Figure 7): The increased operating current Ie(mA) = (VCC - 1.0)/ Re(k) The RSSI output is a current output. It is converted to a voltage by an external resistor connected between Pin 15 and GND. The time constant of the RSSI output is determined by the product of the external converting resistance and the parallel capacitance. When the time constant is longer, the RSSI output response is slower. Determine the external resistance and capacitance by the application. The slope of the RSSI curve characteristics can be changed by changing the external resistance. In this case, the maximum range of converted RSSI output voltage is from GND level to about VCC-0.2 V (the supply voltage minus the collector saturation voltage of the output transistor). In addition, the temperature characteristic of the RSSI output voltage can be changed by changing the temperature characteristic of the external resistor. Normally, the temperature characteristic of the RSSI output voltage is very stable when using a carbon resistor or metal film resistor with a temperature characteristic of 0 to 200 ppm/C.
VCC
Current Output RSSI OUT
I-V Converting Resistor
FIGURE 8: RSSI OUTPUT EQUIVALENT CIRCUIT
VCC VCC VCC
QB
FIGURE 9: FM DETECTOR EQUIVALENT CIRCUIT (4) FM Detector The FM detector is included in the Quadrature FM detector using a Gilbert multiplier. The phase shifter is connected between Pin 10 (IF limiter output) and Pin 11 (detector input), with any available phase shifter. A phase shifter can be used such as the LC resonance circuit, the ceramic discriminator, and the delay line. Figure 11 shows the internal equivalent circuit of the detector. The signal from the phase shifter is applied to the multiplier (in the dotted line) through emitter-follower stage QA. Note that Pin 11 must have the bias voltage impressed from an external source, because Pin 11 is connected with the base of QA only. Because the base of QB of the opposite side is connected with the supply voltage, Pin 11 has to be biased with the equivalent voltage. Using an LC resonance circuit is not a problem (see Figure 10), but attention must be paid when using a ceramic discriminator. If the base voltages are different, the DC voltage of the multiplier does not balance. This alters the DC zero point or worsens the distortion of the demodulation output. The Pin 11 input level should be saturated at the multiplier, if this level is lower, it is easy to disperse the detector output. Therefore, to be in stable operation, the Pin 16 input level should be higher than 100 mVP-P. Figure 10 shows examples of phase shifters. January 2001 TOKO, Inc.
VCC
100
IF OUT Re
200 A
Ie
The emitter-follower operating current can be increased by external resistor Re when the capacitive load is heavy and the waveform distortion will be reduced.
FIGURE 7
Page 20
TK10931V
CIRCUIT DESCRIPTION (CONT.)
Rz is the characteristic impedance
VCC VCC VCC
Rz
Rz
Delay Line
LC Resonance Circuit Ceramic Discriminator
Delay Line
FIGURE 10: EXAMPLES OF PHASE SHIFTERS
(5) AM IF Block The AM IF block is shown in Figure 11. This block is composed of three blocks: the IF AGC amplifier, the AM IF output, and the AM detector. The AGC range is approximately 50 dB.
R3
C5 AM IF-OUT
AGC AMP
VCC
DET
IF-INPUT
C2
R1 R2
AM DET-OUT
C1 C3
AMIF-AGC
C4
FIGURE 11: AM IF EQUIVALENT CIRCUIT The AM IF Input Impedance The AM IF input terminal (Pin 5) is independent of the FM IF input terminal (Pin 7). Respectively different filters for the FM IF and AM IF can be used. The input impedance of the AM IF input terminal (10k) is higher than the FM IF input terminal (1.5 k). Although the AM IF input terminal and the FM IF input terminal are conncected in parallel AC wise, when using common IF filters, it is only necessary to use the FM IF input impedance to determine the termination impedence of the common IF filter. AM IF-AGC Pin 18 is the IF AGC control input terminal. Usually this terminal is connected with the AM detector output terminal (Pin 12) through the ripple filter composed of R1 and C3. The time constant (T = R1 x C3) for the ripple filter is generally selected to be 5 to 10 times larger than the lowest cycle of the AM modulation element. Pin 18 can also be controlled by an external DC source instead of the AM detector output signal. Pin 6 is the decoupling capacitor for the AM IF bias circuit.
January 2001 TOKO, Inc.
Page 21
TK10931V
CIRCUIT DESCRIPTION (CONT.)
VCC
AM IF OUT
VCC/2
Ie
Re
(6) Noise Squelch Circuit This product is equipped with built-in noise squelch circuitry. It is composed of the Filter amplifier, Full-wave Rectifier circuit, and the Comparator. Figure 13 illustrates the Noise Squelch Equivalent Circuit. Figure 14 illustrates the Full-wave Rectifier Circuit. First, the FM detector output is amplified and the noise element is selected by the Band-Pass Filter that is composed with the built-in amplifier. The noise element is rectifed by the built-in full-wave recitifier, resulting in a current output from Pin 21. The current output is filtered and converted to a voltage with resistor R4 and capacitor C3 connected between Pin 21 and GND. The rectified voltage is compared with the built-in reference voltage. The comparator output is provided at Pin 22. Because the comparator output is an open collector output, a pull-up resistor is required. To prevent chatter at the output, the comparator has hysteresis of approximately 70 mV. The Band-Pass Filter is comprised of the built-in filter amplifier for selective noise amplification. Its circuit is the general Sallen-Key type as shown in Figure 13. The constants can be computed as follows. That is C1 = C2 = C F0: Center frequency for BPF Q: Q for BPF Av: Gain for BPF center frequency The rectifier circuit, shown in Figure 14, is implemented with a current output as mentioned previously. The rectification voltage value can be modified by changing the value of the converting resistor R4. The maximum value for its voltage, determined by the power supply voltage, is up to VCC-0.2 V. Since the threshold voltage of the built-in comparator is fixed at 0.7 V, it is possible to adjust the squelch sensitivity by changing the value of R4. In actuality, in order to absorb the deviation for the whole product, the use of a trimmen resistor is recommended. Pick up the noise signal for the detector before the de-emphasis circuit.
FIGURE 12: AM IF OUTPUT EQUIVALENT CIRCUIT AM IF-Output The output from Pin 17 is done through a buffer in front of the AM detector for an AM IF signal that is a fixed amplitude output. Therefore, it is possible to do various applications. This output is an emitter-follower type; the operating current is determined by the resistor connected between the output terminal (Pin 17) and GND. Because the DC voltage at Pin 17 is set up as 1/2 the supply voltage, the operating current can be computed as follows: Ie = VCC/2Re With 22 k (standard value), the operating current is 70 A at VCC = 3 V. Connecting a heavy load increases distortion of the minum half cycle side; decrease the resistance to increase the operating current.
STATUS VCC C2 R5 R4 C3 R3 C1 R2 R1
+ + ~0.7 V VCC/2
FIGURE 13: NOISE SQUELCH EQUIVALENT CIRCUIT
VCC
21
R4
C3
FIGURE 14: FULL-WAVE RECTIFIER EQUIVALENT CIRCUIT Page 22 January 2001 TOKO, Inc.
TK10931V
CIRCUIT DESCRIPTION (CONT.)
(7) AM-ON/OFF Circuit This IC provides an ON/OFF function for the AM block. Because this was necessary for the stand-by state for the AM block, it can be used as a power-save operation. The input part equivalent circuit is shown in Figure 15. By directly controlling the transisor-base as shown in the equivalent circuit, the AM portion ON/OFF input control is possible below a very small current of 50 A. Regarding Pin 14, the AM portion is in operation at 2 V and above; it is in non-operation at 0.2 V and below. In non-operation, the consumption current is down to approximately 2.4 mA. The circuits that can be non-operational in AM OFF are shown as follows. Non-operation circuits: AM IF circuit, AM IF-AGC circuit, AM detector circuit. Always operating circuits: RF-AGC output, Noise squelch circuit, Mixer circuit, Local oscillator circuit, FM IF circuit, FM detector circuit. Feedback through the power supply line from the cold side of the phase shifter is common. To keep the signal level of the phase shifter at its highest, treatment of its cold side is very important. Grounding the cold side with bypass a capacitor is important. Adding a decoupling circuit that uses a CR or LC is effective. An example is shown in Figure 16. Avoid using high resistance values in the offset of the multiplier in the FM detector. When using under about 1 k, there is no effect because the inflow current in Pin 11 is under several A. 3. When the signal is returned to the mixer from the detector, the stability is at its worst. It is ideal that these peripheral components are provided with different sides of a double-sided board and that the reverse side is the GND pattern.
47 F VCC
BIAS
220 to 1 k
0.1 F 0.1 F
50 k AM ON AM OFF
FIGURE 15 (8) Attention to Pattern Layout This product will provide stable operation. However, when using this product, pay attention to the following (1-3) for stable operation because the operating frequency is high. Moreover, the standard application board of this product is shown on page 25. 1. The VCC terminal capacitor is individually grounded by the shortest distance to a GND terminal. VCC Terminal (Pin 4) * GND Terminal (Pin 23) 2. Overall, the IF signal level is higher than other points. Also, this point is the final stage in the limiter amplifier. Therefore, this point easily provides positive feedback to the first stage. Since feedback to the pre-stage depends on radiation, use the shortest distance etch patterns possible. January 2001 TOKO, Inc.
FIGURE 16: EXAMPLE OF STRONG DECOUPLING AROUND THE PHASE SHIFTER
Page 23
CB Radio Application
TK10931V
0.01 F
T2
1
0.01 F 0.01 F
RF INPUT 27 MHz
4
T1
22 pF 1
0.01 F
560
2
4
22 k
0.01 F
SQUELCH COMP OUT VCC 10.7 MHz
50 k in measurement
1k
750
Q4
Q5
1 k
0.1 F
100 k
1 k
Q3
Page 24
AM IF-OUT RSSI OUT
0.01 F
VCC
VCC = 8.0 V
0.1 F RF-AGC CONTROL
10 k
330 6
330 330
0.01 F
20 k
100 pF
100 pF 10 F
Q1
50 6
2 3
0.47 F
10 22 k k
0.022 F
VCC
APPLICATION INFORMATION
8.2 k
10 k
AM DET OUT
0.01 F 7 pF 5.1 k
0.01 F
5.1 k
100 k
033
0.01 F
330 k
0.01 F
1S-1588 *~3
1st OSC 37 MHz * } 0dBm
CFSK107M3
0.01 F
Vref
Vref
15 F
10 k
0.01 F
10 k
0.01 F
MIXER
AM DET
VCC
AM IF
OSC
VCC
2.2 k
44 k
VCC
FM DET
FM IF
5.1 k 4700 pF
33 pF
FM DET-OUT 10 k
100 F
10 k 0.1 F
10.245 MHz
0.1 F
0.1 F 0.1 F
10 pF
30 k
4
100 pF
T3
0.01 F
6
0.01 F
CFU455E 0.01 F
VCC VCC = 8.0 V 47 F
T1 T2 T3 Q1 Q2
: TXXN-22160BU : TXXC-16853N : 7BRE7437Z : 2SC585 : 2SC1675 : 2SC945 Any circuits described herein assume no mass-production. Toko assumes no responsibility for the use of any circuits described herein, conveys no license or other right, and makes no representations that the circuits are free from patent infrigement.
Q3, Q4, Q5
January 2001 TOKO, Inc.
TK10931V
APPLICATION BOARD LAYOUTS
January 2001 TOKO, Inc.
Page 25
TK10931V
PACKAGE OUTLINE
Marking Information
0.35
TSSOP-24
Marking TK10931V 10931
Marki ng
AAAAA YYY
4.4
e 0.65
Recommended Mount Pad
1 Lot. No.
12
1.2 max
0.9
0.50
0 ~ 10
7.8
0 ~ 0.15
e 0.65 0.25
+0.15 -0.05
0.1 6.4 0.12 M
+ 0.3
Dimensions are shown in millimeters Tolerance: x.x = 0.2 mm (unless otherwise specified)
Toko America, Inc. Headquarters 1250 Feehanville Drive, Mount Prospect, Illinois 60056 Tel: (847) 297-0070 Fax: (847) 699-7864
TOKO AMERICA REGIONAL OFFICES
Midwest Regional Office Toko America, Inc. 1250 Feehanville Drive Mount Prospect, IL 60056 Tel: (847) 297-0070 Fax: (847) 699-7864 Western Regional Office Toko America, Inc. 2480 North First Street , Suite 260 San Jose, CA 95131 Tel: (408) 432-8281 Fax: (408) 943-9790 Semiconductor Technical Support Toko Design Center 4755 Forge Road Colorado Springs, CO 80907 Tel: (719) 528-2200 Fax: (719) 528-2375
Visit our Internet site at http://www.tokoam.com
The information furnished by TOKO, Inc. is believed to be accurate and reliable. However, TOKO reserves the right to make changes or improvements in the design, specification or manufacture of its products without further notice. TOKO does not assume any liability arising from the application or use of any product or circuit described herein, nor for any infringements of patents or other rights of third parties which may result from the use of its products. No license is granted by implication or otherwise under any patent or patent rights of TOKO, Inc.
Page 28
(c) 1999 Toko, Inc. All Rights Reserved IC-231-TK11031 0798O0.0K
0.15
+0.15 -0.05
4.8
24
13
1.0
January 2001 TOKO, Inc.
Printed in the USA

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